1 Introduction
In recent years, miniaturized antennas based on metamaterial transmission lines have become the hotspot of current research due to the unique dispersion characteristics of the metamaterial transmission lines. When such an antenna is in a zero-order resonant mode of operation, its operating frequency is independent of the physical size of the antenna. Due to the superior characteristics of the resonant mode, the zero-order resonant frequency of the antenna can be reduced to a very low level, thereby achieving miniaturization. The zero-order resonant antennas of metamaterial transmission lines developed at this stage can be roughly divided into three categories: composite left and right hand transmission line zero-order resonant antennas, negative magnetic permeability zero-order resonant antennas and negative dielectric constant zero-order resonant antennas. The performance superiority requirements for the above different forms of antenna mainly involve the following three aspects, namely: radiation gain, working bandwidth and miniaturization. In view of this, the method of etching the equilateral grooves on the ground to facilitate the resonator to store less electromagnetic energy in the zero-order resonance mode is introduced, which effectively increases the gain of the antenna; on the other hand, how to widen Their working bandwidth also presents a fruitful approach. However, how to design a special-material transmission line zero-order resonant antenna with a more miniaturized degree has not been reported in the related system.
The operating frequency of the zero-order resonant antenna based on the metamaterial transmission line, although independent of the physical electrical size of the antenna, is due to the fact that the antenna itself is composed of transmission line units, so that its resonant frequency is closely related to the specific physical structure of the antenna. It can be seen that how to design a zero-order resonant antenna with miniaturization degree and gain and bandwidth mutual tradeoff is of great significance for future research on such antennas. In this paper, a novel miniaturized negative dielectric constant zero-order resonant antenna based on traditional metamaterial transmission line is successfully designed by loading zigzag lines and parasitic patches. Studies have shown that by changing the size of the parasitic patch, the zero-order resonant mode frequency of the antenna can be adjusted over a large range. This work has certain reference value for the design of special material transmission line antennas with certain space size requirements in the future.
2 Miniaturization of negative dielectric constant zero-order resonant antenna design
In this paper, a miniaturized negative dielectric constant zero-order resonant antenna is designed. The topology is shown in Figure 1. In Fig. 1(a), since the radiation impedance of the antenna is much higher than the characteristic impedance of the feed line by 50 Ω, the antenna adopts a form of coupling feed to make the radiation patch portion of the antenna and the feeder portion are well matched. The radiating patch portion of the antenna is composed of a unit based on a negative dielectric constant transmission line. The metamaterial-based transmission line unit, in addition to the distributed parametric series inductance and parallel capacitance portion of the conventional right-hand transmission line parasitic, has a parallel inductance portion due to the ground via of the patch and the ground.
The specific structural parameters are: L=16.08mm, W=16.08mm, L1=5.49mm, W1=2.18mm, g1=0.11mm, L2=10.48mm, W2=3mm, D=0.8mm, g2=0.1mm, W3=0.1mm, W4=0.2mm; dielectric plate dielectric constant εr=3.38, thickness h=0.8mm
In order to achieve miniaturization of the antenna, we propose to load the parasitic unit in the vicinity of the radiating patch to generate additional capacitance and inductance, in order to reduce the zero-order resonant operating frequency of the antenna under the same overall antenna size, as shown in Figure 1 (a ) The dotted line area. On the one hand, we loaded a parasitic patch of a certain size to create a coupling capacitor. The capacitance generated by this method is referred to as a virtual ground capacitance. On the other hand, a zigzag line is applied between the radiation patch and the parasitic patch to further generate a meander line inductance. Figure 2 shows its equivalent circuit model. Wherein C0 represents the coupling capacitance between the radiation patch and the feeder; the area enclosed by the dotted line is the transmission line model corresponding to the antenna: LR and CR respectively represent the series inductance and the parallel capacitance inherent to the ordinary transmission line; and LLV represents the inductance provided by the ground via hole. ; LLg represents the inductance provided by the meander line; Cg represents the virtual ground capacitance; and R represents the radiation resistance.
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